Hybrid hysteretic control system

ABSTRACT

A system comprises a first comparator, a second comparator, a pulse-width modulation (PWM) controller, and a ramp generator. The first comparator has a positive input coupled to a first ramp output of the ramp generator and a negative input configured to receive an input voltage. The second comparator has a positive input configured to receive the input voltage and a negative input coupled to a second ramp output of the ramp generator. The PWM controller is coupled to outputs and control signal inputs of the first and second comparators and has a control output. In some implementations, the ramp generator generates a high-side falling ramp for the first comparator and a low-side rising ramp for the second comparator. In some implementations, the ramp generator includes a first ramp generator for the high-side falling ramp and a second ramp for the low-side rising ramp.

BACKGROUND

Hybrid hysteretic control (HHC) systems are used to improve thetransient response of power supply units by simplifying the compensationinto a first order system. Two-sided HHC provides faster transientresponse times than one-sided HHC, but is implemented with an externalcomparator and ramp generator, increasing the area occupied by the HHCsystem on the integrated circuit including the HHC system and the powerconverter. In addition, unavoidable differences between the two feedbacksignal chains can introduce imbalance and asymmetry in the resultingpulse width modulation control signals.

SUMMARY

A system comprises a first comparator, a second comparator, apulse-width modulation (PWM) controller, and a ramp generator. The firstcomparator has a positive input coupled to a first ramp output of theramp generator and a negative input configured to receive an inputvoltage. The second comparator has a positive input configured toreceive the input voltage and a negative input coupled to a second rampoutput of the ramp generator. The PWM controller is coupled to outputsand control signal inputs of the first and second comparators and has acontrol output.

In some implementations, the ramp generator generates a first ramp forthe first comparator and a second ramp for the second comparator. Thefirst ramp can be a high-side falling ramp, and the second ramp can be alow-side rising ramp. In some implementations, the ramp generatorincludes a first ramp generator for the high-side falling ramp and asecond ramp for the low-side rising ramp. The first and second ramps areoffset by half a period T.

In some implementations, a voltage sensing circuit provides the inputvoltage. The input voltage is a first input voltage in someimplementations, and the control output of the PWM comprises a firstcontrol output and a second control output. The system also includes afirst transistor, a second transistor, a third transistor, a fourthtransistor, a capacitor, an inductor, and a transformer. The firsttransistor has a first control terminal coupled to the first controloutput and first and second current terminals. The second transistor hasa second control terminal coupled to the second control output and thirdand fourth current terminals. The third current terminal is coupled tothe second current terminal, and the first and fourth current terminalsreceive a second input voltage.

The capacitor has a first capacitor terminal coupled to the fourthcurrent terminal and a second capacitor terminal. The voltage sensingcircuit measures the first input voltage across the capacitor. Theinductor has a first inductor terminal coupled to the second and thirdcurrent terminals and a second inductor terminal. The transformer has afirst input coupled to the second inductor terminal and a second inputcoupled to the second capacitor terminal. The transformer also has threetransformer outputs.

The third transistor has a third control terminal configured to receivea biasing voltage, a fifth current terminal coupled to the firsttransformer output, and a sixth current terminal. The fourth transistorhas a fourth control terminal configured to receive the biasing voltage,a seventh current terminal coupled to the second transformer output, andan eighth current terminal coupled to the sixth current terminal. Insome implementations, the transformer is a center-tap transformer.

BRIEF DESCRIPTION OF THE DRAWINGS

For a detailed description of various examples, reference will now bemade to the accompanying drawings in which:

FIG. 1A shows a block diagram of an example LLC converter andcorresponding one-sided hybrid hysteretic control (HHC) system.

FIG. 1B shows waveforms of signals generated in the one-sided HHC systemshown in FIG. 1A.

FIG. 2A shows a block diagram of an example two-sided HHC system for theLLC converter shown in FIG. 1A.

FIG. 2B shows waveforms of signals generated in the two-sided HHC systemshown in FIG. 2A.

FIG. 3A shows a block diagram of an example two-sided HHC system for theLLC converter shown in FIG. 1A.

FIG. 3B shows waveforms of signals generated in the two-sided HHC systemshown in FIG. 3A.

FIG. 4A shows a block diagram of an example peak current-mode controlDC-DC converter for the two-sided HHC system shown in FIG. 3A.

FIG. 4B shows waveforms of signals in the peak current-mode controlDC-DC converter shown in FIG. 4A and the two-sided HHC system shown inFIG. 3A.

FIG. 4C shows a graph of the average current over duty cycle for thepeak current-mode control DC-DC converter shown in FIG. 4A.

The same reference number is used in the drawings for the same orsimilar (either by function and/or structure) features.

DETAILED DESCRIPTION

The described digital two-sided hybrid hysteretic control (HHC) systemsinclude two comparators, two ramp generators, and a pulse-widthmodulation (PWM) controller. Each comparator has a positive input, anegative input, a control input, and an output. In the first comparator,the positive input receives a high-side falling ramp from a rampgenerator, and the negative input receives a voltage across a resonantcapacitor in a power converter. The control input receives a firstfeedback signal from the PWM controller. In the second comparator, thepositive input receives the voltage across the resonant capacitor, andthe negative input receives a low-side rising ramp from the other rampgenerator. The control input receives a second feedback signal from thePWM controller, which generates first and second control signals for thepower converter based on the outputs of the first and secondcomparators. The digital two-sided HHC systems are integrated into asingle semiconductor die and use both rising and falling ramps, insteadof a falling ramp only.

FIG. 1A shows a block diagram of an example LLC converter 100 andcorresponding one-sided hybrid hysteretic control (HHC) system 150. TheLLC converter 100 includes transistors MA, MB, MC, and MD; resonantcapacitor C 115, inductor L 120, transformer 130, voltage sensingcircuit 125, and the one-sided HHC system 150. The voltage sensingcircuit 125 is configured to measure the voltage across the resonantcapacitor C 115. In some implementations, the transformer 130 is acenter-tap transformer. The one-sided HHC system 150 includes acomparator 160, a pulse-width modulation (PWM) controller 170, ananalog-to-digital converter (ADC) 174, an adder 180, and a rampgenerator 185.

The transistors MA, MB, MC, and MD may be metal oxide semiconductorfield-effect transistors (MOSFETs). Accordingly, MA-MD are n-typeMOSFETs (NMOS) in an example. In other examples, one or more of MA-MDare p-type MOSFETs (PMOS) or bipolar junction transistors (BJTs). A BJTincludes a base corresponding to the gate terminal of a MOSFET, and acollector and an emitter corresponding to the drain and source terminalsof a MOSFET. The base of a BJT and the gate terminal of a MOSFET arealso called control inputs. The collector and emitter of a BJT and thedrain and source terminals of a MOSFET are also called currentterminals.

The source terminal of MA and the drain terminal of MB are coupledtogether, and the input voltage Vin 105 is applied across the drainterminal of MA and the source terminal of MB. The gate terminal of MA isconfigured to receive the first control signal CTLA 110A, and the gateterminal of MB is configured to receive the second control signal CTLB110B. The inductor L 120 has a first terminal coupled to the sourceterminal of MA and the drain terminal of MB and a second terminalcoupled to the transformer 130. The resonant capacitor C 115 has a firstterminal coupled to the source terminal of MB and a second terminalcoupled to the transformer 130. The voltage sensing circuit 125 iscoupled to the second terminal of the resonant capacitor C 115 andmeasures the voltage VCR 155 across the resonant capacitor C 115.

The transformer 130 includes a primary winding 134 and a secondarywinding 138. The second terminal of the inductor L 120 is coupled to afirst terminal of the primary winding 134, and the second terminal ofthe resonant capacitor C 115 is coupled to a second terminal of theprimary winding 134. A first terminal of the secondary winding 138 iscoupled to the drain terminal of MD, and a second terminal of thesecondary winding 138 is coupled to the drain terminal of MC. The sourceterminals of MC and MD are coupled together, and the gate terminals ofMC and MD are configured to receive a biasing voltage Vbias 140. Theoutput voltage Vout 145 is taken across the center tap of transformer130 and the source terminals of MC and MD.

In the one-sided HHC system 150, the comparator 160 has a first inputconfigured to receive the voltage VCR 155 across the resonant capacitorC 115 from the voltage sensing circuit 125, and a second input coupledto an output of the ramp generator 185 to receive the ramp 190. Thecomparator 160 is also configured to receive a feedback signal FDBK 168from the PWM controller 170, which resets a digital-to-analog converter(DAC) of the comparator 160 to support HHC. The output 164 of comparator160 is provided to the PWM controller 170, which outputs the controlsignals CTLA 110A and CTLB 110B for transistors MA and MB, respectively,as well as the feedback signal FDBK 168 for the comparator 160. The ADC174 receives the output voltage Vout 145, and adder 180 subtracts theoutput of the ADC 174 from a reference signal Vref 178, which representsthe target output voltage. A voltage controller 183 receives thedifference between the target output voltage represented by Vref 178 andthe digitized output voltage from ADC 174, and generates a controlsignal for the ramp generator 185. The ramp generator 185 receives thecontrol signal from the voltage controller 183 and generates the rampsignal 190. In some implementations, the control signal from the voltagecontroller 183 indicates the initial value of the ramp signal 190.

FIG. 1B shows waveforms of signals generated in the one-sided HHC system150 shown in FIG. 1A. At time t0, the control signal CTLA 110Atransitions from logic low to logic high, and the control signal CTLB110B transitions from logic high to logic low. The VCR 155 intersectswith the ramp signal 190 at time t1, triggering the control signal CTLB110B to transition from logic low to logic high. CTLB 110B is logic highand CTLA 110A is logic low from time t1 to time t2, at which CTLB 110Btransitions to logic low and CTLA 110A transitions to logic high. Thelength of time between time t0 and t1 while CTLA 110A is logic high ismeasured, and the time t2 is chosen such that the length of time betweent1 and t2 while CTLB 110B is logic low is kept equal to the length oftime between t0 and t1. At time t3, the VCR 155 intersects with the ramp190, and the control signal CTLB 110B transitions from logic low tologic high. The time between t1 and t3 is a period T 195. However,one-sided HHC can have slower transient response times than two-sidedHHC, shown in FIG. 2A.

FIG. 2A shows a block diagram of an example analog two-sided HHC system250 that may be used in place of one-sided HHC system 150 in the LLCconverter 100 shown in FIG. 1A. For ease of explanation, the analogtwo-sided HHC system 250 is described herein with respect to the LLCconverter shown in FIG. 1A, and includes an inverter 210, twocomparators 260A-B, a pulse-width modulation (PWM) controller 270, anADC 274, an adder 280, and a ramp generator 285. The comparator 260A hasa positive input that receives a first ramp 290A from the ramp generator285 and a negative input that receives the voltage VCR 155 across theresonant capacitor C 115. The comparator 260A also receives a feedbacksignal FDBK 268A from the PWM controller 270 and generates an outputsignal TRIPA 264A, which is provided to the PWM controller 270.

The inverter 210 receives the voltage VCR 155 and outputs the inverse,VCR 255 to a negative input of comparator 260B. The positive input ofcomparator 260B receives a second ramp 290B from the ramp generator 285.The comparator 260B also receives a feedback signal FDBK 268B from thePWM controller 270 and generates an output signal TRIPB 264B, which isprovided to the PWM controller 270. The PWM controller 270 generates thefeedback signals FDBK 268A and 268B for comparator 260A and 260B,respectively, to reset the DACs in comparators 260A and 260B. The PWMcontroller 270 outputs the control signals CTLA 110A and CTLB 110B fortransistors MA and MB, respectively, in the LLC converter 100 shown inFIG. 1A.

The ADC 274 receives the output voltage Vout 145, and adder 280subtracts the output of the ADC 274 from a reference signal Vref 278,which represents the target output voltage. A voltage controller 283receives the difference between the target output voltage represented byVref 278 and the digitized output voltage from ADC 274 and generates acontrol signal for ramp generator 285. The ramp generator 285 receivesthe control signal from the voltage controller 283 and generates theramps 290A and 290B for the comparators 260A and 260B, respectively. Insome implementations, the control signal from the voltage controller 283indicates the initial values for ramps 290A and 290B. FIG. 2B showswaveforms of signals generated in the two-sided HHC system 250 shown inFIG. 2A, including the ramp 290A relative to VCR 155, the ramp 290Brelative to VCR 255, and the control signals CTLA 110A and CTLB 110B.

Ramp 290B is offset from ramp 290A by half a period T 295 of the ramp290B, and at time t1, VCR 255 intersects with ramp 290B, causing CTLB110B to transition from logic high to logic low and CTLA 110A totransition from logic low to logic high. At time t2, VCR 155 intersectswith ramp 290A, causing CTLA 110A to transition from logic high to logiclow and CTLB 110B to transition from logic low to logic high. At t3, VCR255 intersects with ramp 290B, causing CTLB 110B to transition fromlogic high to logic low and CTLA 110A to transition from logic low tologic high.

At time t4, VCR 155 intersects with ramp 290A, causing CTLA 110A totransition from logic high to logic low and CTLB 110B to transition fromlogic low to logic high. The analog two-sided HHC system 250 offersfaster transient response times than one-sided HHC system 150 bututilizes an analog inverter 210 to generate the second feedback signalVCR 255, which can introduce error or delays into the resulting outputsignal TRIPB 264B from comparator 260B. In addition, the ramp generator285 is external to the integrated circuit including the comparators 260Aand 260B and PWM controller 270, occupying additional area.

FIG. 3A shows a block diagram of an example digital two-sided HHC system350 that may be used in place of one-sided HHC system 150 in the LLCconverter 100 shown in FIG. 1A. For ease of explanation, the digitaltwo-sided HHC system 350 is described herein with respect to the LLCconverter 100 shown in FIG. 1A, and includes two comparators 360A-B, aPWM controller 370, an ADC 374, an adder 380, a voltage controller 383,and a ramp generator 385. The comparator 360A has a positive input thatreceives a high-side falling ramp RAMP_H 390A from the ramp generator385 and a negative input that receives the voltage VCR 155 across theresonant capacitor C 115. The comparator 360A also receives a feedbacksignal FDBK 368A from the PWM controller 370 and generates an outputsignal TRIP_H 364A, which is provided to the PWM controller 370.

The comparator 360B has a positive input that receives the voltage VCR155 across the resonant capacitor C 115 and a negative input thatreceives a low-side rising ramp RAMP_L 390B from the ramp generator 385.The comparator 360B also receives a feedback signal FDBK 368B from thePWM controller 370 and generates an output signal TRIP_L 364B, which isprovided to the PWM controller 370. The PWM controller 370 generates thefeedback signals FDBK 368A and 368B for comparator 360A and 360B,respectively. The PWM controller 370 outputs the control signals CTLA110A and CTLB 110B for transistors MA and MB, respectively, in the LLCconverter 100 shown in FIG. 1A.

The ADC 374 receives the output voltage Vout 145, and adder 380subtracts the output of the ADC 374 from a reference voltage Vref 378,which represents the target output voltage. A voltage controller 383receives the difference between the target output voltage represented byVref 378 and the digitized output voltage from ADC 374, and generates acontrol signal for the ramp generator 385. The ramp generator 385receives control signal from the voltage controller 383 and generatesthe high-side falling ramp RAMP_H 390A and the low-side rising rampRAMP_L 390B for the comparators 360A and 360B, respectively. In someimplementations, the control signal from the voltage controller 383indicates the initial values of the ramp signals RAMP_H 390A and RAMP_L390B. The ramp generator 385 uses preset slopes for each of RAMP_H 390Aand RAMP_L 390B, and the feedback signals FDBK 368A and 368B reset thecomparator DACs in comparator 360A and 360B to cut off the ramps RAMP_H390A and RAMP_L 390B.

FIG. 3B shows waveforms of signals generated in the digital two-sidedHHC system 350 shown in FIG. 3A, including the high-side ramp RAMP_H390A and the low-side ramp RAMP_L 390B relative to VCR 155, and thecontrol signals CTLA 110A and CTLB 110B. The low-side ramp RAMP_L 390Bis offset from the high-side ramp RAMP_H 390A by half a period T 395 ofthe ramps 390A and 390B, and at time t1, VCR 155 intersects withlow-side ramp RAMP_L 390B, causing CTLB 110B to transition from logichigh to logic low and CTLA 110A to transition from logic low to logichigh. At time t2, VCR 155 intersects with high-side ramp RAMP_H 390A,causing CTLA 110A to transition from logic high to logic low, and CTLB110B to transition from logic low to logic high. At time t3, VCR 155intersects with low-side ramp RAMP_L 390B, causing CTLB 110B totransition from logic high to logic low and CTLA 110A to transition fromlogic low to logic high. At time t4, VCR 155 intersects with high-sideramp RAMP_H 390A, causing CTLA 110A to transition from logic high tologic low, and CTLB 110B to transition from logic low to logic high.

The digital two-sided HHC system 350 offers the faster transientresponse times of a two-sided HHC system relative to one-sided HHCsystems and also offers reduced PWM asymmetry compared to the analogtwo-sided HHC system 250 shown in FIG. 2A by triggering transitions inCTLA 110A and CTLB 110B based on both the high side and the low side ofVCR 155. In addition, the ramp generator 385 is included in theintegrated circuit with the comparators 360A-B, PWM controller 370, andthe remaining components of digital two-sided HHC system 350.

The digital two-sided HHC system 350 shown in FIG. 3A can be used tosupport advanced topologies such as peak boost converters, peak buckconverters, valley boost converters, valley buck converters, and thelike. To illustrate, FIG. 4A shows a block diagram of an example peakcurrent-mode control (PCMC) DC-DC converter 400 that can be controlledby the digital two-sided HHC system shown in FIG. 3A. The PCMC DC-DCconverter 400 includes transistors MA and MB, capacitors C 415 and C430, and inductor L 420. The transistors MA and MB are NMOS in thisexample. In other examples, one or more of MA and MB are PMOS or BJTs.

The capacitor C 415 has a first terminal coupled to a first terminal ofthe inductor L 420, and a second terminal. The input voltage Vin 405 isapplied to the first and second terminals of the capacitor C 415 and thefirst terminal of the inductor L 420. The second terminal of theinductor L 420 is coupled to the drain terminal of MA and the sourceterminal of MB. A current iL 425 flows through the inductor L 420. Thesource terminal of MA is coupled to the second terminal of the capacitorC 415, and the gate terminal of MA is configured to receive the firstcontrol signal CTLA 410A. The drain terminal of MB is coupled to a firstterminal of the capacitor C 430, and the gate terminal of MB isconfigured to receive the second control signal CTLB 410B. The capacitorC 430 has a second terminal coupled to the source terminal of MA and thesecond terminal of the capacitor C 415. The output voltage Vout 445 istaken across the capacitor C 430.

The digital two-sided HHC system 350 shown in FIG. 3A can be used toprovide the control signals CTLA 410A and CTLB 410B. FIG. 4B showswaveforms of the current iL 425 through the inductor L 420 shown in thePCMC DC-DC converter 400 shown in FIG. 4A and the high side falling rampRAMP_H 490A and the low side rising ramp RAMP_L 490B generated in thedigital two-sided HHC system used to generate the control signals CTLA410A and CTLB 410B.

At time t1, the current iL 425 intersects with the high side fallingramp RAMP_H 490A, and the control system generates the control signalsCTLA 410A and CTLB 410B such that iL 425 decreases. At time t2, iL 425increases again, and at time t3, iL 425 intersects the high side fallingramp RAMP_H 490A, and the control system generates the control signalsCTLA 410A and CTLB 410B such that iL 425 decreases. At time t4, thecurrent iL 425 intersects with the low side rising ramp RAMP_L 490B, andthe control system generates the control signals CTLA 410A and CTLB 410Bsuch that the current iL 425 increases. At time t5, the current iL 425decreases again, and at time t6, iL 425 intersects with the low siderising ramp RAMP_L 490B, and the control system generates the controlsignals CTLA 410A and CTLB 410B such that the current iL 425 increases.

FIG. 4C shows a graph of the average current lo 450 over duty cycle Dfor the PCMC DC-DC converter 400 shown in FIG. 4A. During a first timeperiod Tcharge 455, the capacitors C 415 and 430 are charged, and at theduty cycle Do 465, the average current lo 450 changes directions and thecapacitors C 415 and 430 begin to discharge for a time period Tdischarge460. The duty cycle Do 465 may be represented as:

${{Do}465} = {1 - \frac{{Vin}405}{{Vout}445}}$

In this description, the term “couple” may cover connections,communications, or signal paths that enable a functional relationshipconsistent with this description. For example, if device A generates asignal to control device B to perform an action: (a) in a first example,device A is coupled to device B by direct connection; or (b) in a secondexample, device A is coupled to device B through intervening component Cif intervening component C does not alter the functional relationshipbetween device A and device B, such that device B is controlled bydevice A via the control signal generated by device A.

A device that is “configured to” perform a task or function may beconfigured (e.g., programmed and/or hardwired) at a time ofmanufacturing by a manufacturer to perform the function and/or may beconfigurable (or re-configurable) by a user after manufacturing toperform the function and/or other additional or alternative functions.The configuring may be through firmware and/or software programming ofthe device, through a construction and/or layout of hardware componentsand interconnections of the device, or a combination thereof.

As used herein, the terms “terminal”, “node”, “interconnection”, “pin”and “lead” are used interchangeably. Unless specifically stated to thecontrary, these terms are generally used to mean an interconnectionbetween or a terminus of a device element, a circuit element, anintegrated circuit, a device or other electronics or semiconductorcomponent.

A circuit or device that is described herein as including certaincomponents may instead be adapted to be coupled to those components toform the described circuitry or device. For example, a structuredescribed as including one or more semiconductor elements (such astransistors), one or more passive elements (such as resistors,capacitors, and/or inductors), and/or one or more sources (such asvoltage and/or current sources) may instead include only thesemiconductor elements within a single physical device (e.g., asemiconductor die and/or integrated circuit (IC) package) and may beadapted to be coupled to at least some of the passive elements and/orthe sources to form the described structure either at a time ofmanufacture or after a time of manufacture, for example, by an end-userand/or a third-party.

While the use of particular transistors is described herein, othertransistors (or equivalent devices) may be used instead. For example, ap-type metal-oxide-silicon field effect transistor (“MOSFET”) may beused in place of an n-type MOSFET with little or no changes to thecircuit. Furthermore, other types of transistors may be used (such asbipolar junction transistors (BJTs)).

Circuits described herein are reconfigurable to include additional ordifferent components to provide functionality at least partially similarto functionality available prior to the component replacement.Components shown as resistors, unless otherwise stated, are generallyrepresentative of any one or more elements coupled in series and/orparallel to provide an amount of impedance represented by the resistorshown. For example, a resistor or capacitor shown and described hereinas a single component may instead be multiple resistors or capacitors,respectively, coupled in parallel between the same nodes. For example, aresistor or capacitor shown and described herein as a single componentmay instead be multiple resistors or capacitors, respectively, coupledin series between the same two nodes as the single resistor orcapacitor.

Unless otherwise stated, “about,” “approximately,” or “substantially”preceding a value means+/−10 percent of the stated value. Modificationsare possible in the described examples, and other examples are possiblewithin the scope of the claims.

1. A system, comprising: a first comparator having a first positiveinput, a first negative input, a first control input, and a firstoutput, wherein the first negative input is configured to receive aninput voltage; a second comparator having a second positive input, asecond negative input, a second control input, and a second output,wherein the second positive input is configured to receive the inputvoltage; a pulse-width modulation (PWM) controller coupled to the firstand second outputs and the first and second control inputs and having acontrol output and feedback outputs coupled to the first control inputof the first comparator and the second control input of the secondcomparator; and a ramp generator having a first ramp output coupled tothe first positive input and a second ramp output coupled to the secondnegative input.
 2. The system of claim 1, wherein the ramp generator isconfigured to generate a first ramp for the first comparator and asecond ramp for the second comparator, wherein the first ramp is ahigh-side falling ramp, and wherein the second ramp is a low-side risingramp.
 3. The system of claim 2, wherein the ramp generator comprises: afirst ramp generator having the first ramp output and configured togenerate the first ramp for the first comparator; and a second rampgenerator having the second ramp output and configured to generate thesecond ramp for the second comparator.
 4. The system of claim 2, whereinthe first and second ramps are offset by half a period T.
 5. The systemof claim 2, wherein a first control signal generated by the PWMcontroller and provided to the first control input causes the first rampto reset, and wherein a second control signal generated by the PWMcontroller and provided to the second control input causes the secondramp to reset.
 6. The system of claim 1, further comprising a voltagesensing circuit configured to provide the input voltage.
 7. The systemof claim 6, wherein the input voltage is a first input voltage, whereinthe control output comprises a first control output and a second controloutput, the system further comprising: a first transistor having a firstcontrol terminal coupled to the first control output, a first currentterminal, and a second current terminal; a second transistor having asecond control terminal coupled to the second control output, a thirdcurrent terminal coupled to the second current terminal, and a fourthcurrent terminal, wherein the first and fourth current terminals areconfigured to receive a second input voltage; a capacitor having a firstcapacitor terminal coupled to the fourth current terminal and a secondcapacitor terminal, wherein the voltage sensing circuit is configured tomeasure the first input voltage across the capacitor; an inductor havinga first inductor terminal coupled to the second and third currentterminals and a second inductor terminal; a transformer having a firstinput coupled to the second inductor terminal, a second input coupled tothe second capacitor terminal, a first transformer output, a secondtransformer output, and a third transformer output; a third transistorhaving a third control terminal configured to receive a biasing voltage,a fifth current terminal coupled to the first transformer output, and asixth current terminal; and a fourth transistor having a fourth controlterminal configured to receive the biasing voltage, a seventh currentterminal coupled to the second transformer output, and an eighth currentterminal coupled to the sixth current terminal.
 8. The system of claim7, wherein the transformer is a center-tap transformer.
 9. The system ofclaim 7, further comprising: an analog-to-digital converter (ADC)configured to receive a voltage across the third transformer output andthe sixth and eighth current terminals and having an output; an adderhaving a positive input configured to receive a reference signal, anegative input coupled to the ADC output, and an output; and a voltagecontroller having an input coupled to the adder output and an outputcoupled to the ramp generator.
 10. The system of claim 9, wherein: Theramp generator is configured to generate a first ramp for the firstcomparator and a second ramp for the second comparator; and the voltagecontroller is configured to indicate a first initial frequency for thefirst ramp and a second initial frequency for the second ramp.
 11. Adevice, comprising: a first comparator having a positive inputconfigured to receive a first ramp and a negative input configured toreceive an input voltage, wherein the first comparator is configured togenerate a first triggering signal; a second comparator having apositive input configured to receive the input voltage and a negativeinput configured to receive a second ramp, wherein the second comparatoris configured to generate a second triggering signal; a pulse-widthmodulation (PWM) controller having feedback outputs coupled to the firstcomparator and the second comparator and configured to: receive thefirst triggering signal from the first comparator and the secondtriggering signal from the second comparator; generate a first controlsignal and a second control signal based on the first and secondtriggering signals; and a ramp generator configured to generate thefirst ramp for the first comparator and the second ramp for the secondcomparator.
 12. The device of claim 11, wherein the first ramp is ahigh-side falling ramp and the second ramp is a low-side rising ramp.13. The device of claim 12, wherein the first and second ramps areoffset by half a period T.
 14. The device of claim 11, wherein: thefirst comparator further comprises a first control input configured toreceive a first feedback signal; and the second comparator furthercomprises a second control input configured to receive a second feedbacksignal.
 15. The device of claim 14, wherein the PWM controller isfurther configured to generate the first feedback signal for the firstcomparator and the second feedback signal for the second comparator. 16.The device of claim 11, wherein the input voltage is a first inputvoltage, the device further comprising: a first transistor having acontrol terminal configured to receive the first control signal, a firstcurrent terminal, and a second current terminal; a second transistorhaving a control terminal configured to receive the second controlsignal, a third current terminal coupled to the second current terminal,and a fourth current terminal, wherein the first and fourth currentterminals are configured to receive a second input voltage; atransformer having a first transformer input, a second transformerinput, a first transformer output, a second transformer output, and athird transformer output; a capacitor coupled between the fourth currentterminal and the second transformer input; a voltage sensing circuitconfigured to measure the first input voltage across the capacitor; aninductor coupled between the second and third current terminals and thesecond transformer input; a third transistor having a control terminalconfigured to receive a biasing voltage, a fifth current terminalcoupled to the first transformer output, and a sixth current terminal;and a fourth transistor having a control terminal configured to receivethe biasing voltage, a seventh current terminal coupled to the secondtransformer output, and an eighth current terminal coupled to the sixthcurrent terminal.
 17. The device of claim 16, wherein the transformer isa center-tap transformer.
 18. The device of claim 11, furthercomprising: a first transistor having a control terminal configured toreceive the first control signal, a first current terminal, and a secondcurrent terminal; a second transistor having a control terminalconfigured to receive the second control signal, a third currentterminal, and a fourth current terminal coupled to the first currentterminal; a capacitor having a first capacitor terminal coupled to thesecond current terminal and a second capacitor terminal; an inductorhaving a first inductor terminal coupled to the second capacitorterminal and a second inductor terminal coupled to the first and fourthcurrent terminals; and a voltage sensing circuit configured to measure avoltage across the capacitor.
 19. An apparatus, comprising: a firstcomparator having a positive input configured to receive a high-sidefalling ramp and a negative input configured to receive an inputvoltage, wherein the first comparator is configured to generate a firsttriggering signal; a second comparator having a positive inputconfigured to receive the input voltage and a negative input configuredto receive a low-side rising ramp, wherein the second comparator isconfigured to generate a second triggering signal, wherein the high-sidefalling ramp and the low-side rising ramp are offset by half a period T;a pulse-width modulation (PWM) controller having feedback outputscoupled to the first comparator and the second comparator and configuredto: receive the first triggering signal from the first comparator andthe second triggering signal from the second comparator; generate afirst control signal and a second control signal based on the first andsecond triggering signals; and a ramp generator configured to generatethe high-side falling ramp and the low-side rising ramp.
 20. Theapparatus of claim 19, wherein: the first comparator further comprises afirst control input configured to receive a first feedback signal; andthe second comparator further comprises a second control inputconfigured to receive a second feedback signal.
 21. The apparatus ofclaim 20, wherein the PWM controller is further configured to generatethe first feedback signal for the first comparator and the secondfeedback signal for the second comparator.